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QT113H-IS

型号：

QT113H-IS

描述：

电荷转移触摸传感器[ CHARGE-TRANSFER TOUCH SENSOR ]

品牌：

ETC[ ETC ]

页数：

12 页

PDF大小：

179 K

下载PDF手册
QProx™ QT113 / QT113H  
CHARGE-TRANSFER TOUCH SENSOR  
! Projects a proximity field through air  
! Less expensive than many mechanical switches  
! Sensitivity easily adjusted via capacitor value  
! Turns small objects into intrinsic touch sensors  
! 100% autocal for life - no adjustments required  
! 2.5 to 5V, 600µA single supply operation  
! Toggle mode for on/off control (strap option)  
! 10s, 60s, infinite auto-recal timeout (strap options)  
! Gain settings in 2 discrete levels  
Vdd  
Out  
1
2
3
4
8
7
6
5
Vss  
Sns2  
Sns1  
Gain  
Opt1  
Opt2  
! HeartBeat™ health indicator on output  
! Active-low (QT113) or active-high outputs (QT113H)  
! Only one external part required - a 1¢ capacitor  
APPLICATIONS -  
! Light switches  
! Prox sensors  
! Appliance control  
! Security systems  
! Access systems  
! Pointing devices  
! Elevator buttons  
! Toys & games  
The QT113 charge-transfer (“QT’”) touch sensor is a self-contained digital IC capable of detecting near-proximity or touch. It will  
project a proximity sense field through air, via almost any dielectric, like glass, plastic, stone, ceramic, and most kinds of wood. It can  
also turn small metal-bearing objects into intrinsic sensors, making them responsive to proximity or touch. This capability coupled with  
its ability to self calibrate continuously can lead to entirely new product concepts.  
It is designed specifically for human interfaces, like control panels, appliances, toys, lighting controls, or anywhere a mechanical  
switch or button may be found; it may also be used for some material sensing and control applications provided that the presence  
duration of objects does not exceed the recalibration timeout interval.  
The QT113 requires only a common inexpensive capacitor in order to function.  
Power consumption is only 600µA in most applications. In most cases the power supply need only be minimally regulated, for example  
by Zener diodes or an inexpensive 3-terminal regulator.  
The QT113’s RISC core employs signal processing techniques pioneered by Quantum; these are specifically designed to make the  
device survive real-world challenges, such as ‘stuck sensor’ conditions and signal drift. Even sensitivity is digitally determined and  
remains constant in the face of large variations in sample capacitor CS and electrode CX. No external switches, opamps, or other  
analog components aside from CS are usually required.  
The option-selectable toggle mode permits on/off touch control, for example for light switch replacement. The Quantum-pioneered  
HeartBeat™ signal is also included, allowing a host microcontroller to monitor the health of the QT113 continuously if desired. By  
using the charge transfer principle, the IC delivers a level of performance clearly superior to older technologies in a highly  
cost-effective package.  
AVAILABLE OPTIONS  
TA  
SOIC  
8-PIN DIP  
00C to +700C  
00C to +700C  
-400C to +850C  
-400C to +850C  
QT113-S  
QT113H-S  
QT113-IS  
QT113H-IS  
QT113-D  
QT113H-D  
-
-
Quantum Research Group Ltd  
Copyright Quantum Research Group Ltd  
R1.10/0104  
Figure 1-1 Standard mode options  
1 - OVERVIEW  
+2.5 to 5  
The QT113 is a digital burst mode charge-transfer (QT)  
sensor designed specifically for touch controls; it includes all  
hardware and signal processing functions necessary to  
provide stable sensing under a wide variety of changing  
conditions. Only a single low cost, non-critical capacitor is  
required for operation.  
SENSING  
ELECTRODE  
1
Vdd  
2
3
4
7
5
6
OUT  
SNS2  
GAIN  
SNS1  
Figure 1-1 shows the basic QT113 circuit using the device,  
with  
a
conventional output drive and power supply  
Cs  
connections.  
OPT1  
OPT2  
10nF  
Cx  
1.1 BASIC OPERATION  
The QT113 employs bursts of charge-transfer cycles to  
acquire its signal. Burst mode permits power consumption in  
Vss  
OUTPUT=DC  
the microamp range, dramatically reduces RF emissions, TIMEOUT=10 Secs  
8
TOGGLE=OFF  
lowers susceptibility to EMI, and yet permits excellent  
GAIN=HIGH  
response time. Internally the signals are digitally processed  
to reject impulse noise, using a 'consensus' filter which  
requires three consecutive confirmations of a detection  
before the output is activated.  
1.2 ELECTRODE DRIVE  
The internal ADC treats Cs as a floating transfer capacitor; as  
a direct result, the sense electrode can be connected to  
either SNS1 or SNS2 with no performance difference. In both  
cases the rule Cs >> Cx must be observed for proper  
operation. The polarity of the charge buildup across Cs  
during a burst is the same in either case.  
The QT switches and charge measurement hardware  
functions are all internal to the QT113 (Figure 1-2). A 14-bit  
single-slope switched capacitor ADC includes both the  
required QT charge and transfer switches in a configuration  
that provides direct ADC conversion. The ADC is designed to  
dynamically optimize the QT burst length according to the  
rate of charge buildup on Cs, which in turn depends on the  
values of Cs, Cx, and Vdd. Vdd is used as the charge  
reference voltage. Larger values of Cx cause the charge  
transferred into Cs to rise more rapidly, reducing available  
resolution; as a minimum resolution is required for proper  
operation, this can result in dramatically reduced apparent  
gain. Conversely, larger values of Cs reduce the rise of  
differential voltage across it, increasing available resolution  
by permitting longer QT bursts. The value of Cs can thus be  
increased to allow larger values of Cx to be tolerated (Figures  
4-1, 4-2, 4-3 in Specifications, rear).  
It is possible to connect separate Cx and Cx’ loads to SNS1  
and SNS2 simultaneously, although the result is no different  
than if the loads were connected together at SNS1 (or  
SNS2). It is important to limit the amount of stray capacitance  
on both terminals, especially if the load Cx is already large,  
for example by minimizing trace lengths and widths so as not  
to exceed the Cx load specification and to allow for a larger  
sensing electrode size if so desired.  
The PCB traces, wiring, and any components associated with  
or in contact with SNS1 and SNS2 will become touch  
sensitive and should be treated with caution to limit the touch  
area to the desired location. Multiple touch electrodes can be  
used, for example to create a control button on both sides of  
an object, however it is impossible for the sensor to  
distinguish between the two touch areas.  
The IC is responsive to both Cx and Cs, and changes in Cs  
can result in substantial changes in sensor gain.  
Option pins allow the selection or alteration of several special  
features and sensitivity.  
1.3 ELECTRODE DESIGN  
Figure 1-2 Internal Switching & Timing  
1.3.1 ELECTRODE GEOMETRY AND SIZE  
There is no restriction on the shape of  
ELECTRODE  
the electrode; in most cases common  
sense and a little experimentation can  
result in a good electrode design. The  
QT113 will operate equally well with  
long, thin electrodes as with round or  
square ones; even random shapes are  
Result  
SNS2  
C
s
acceptable. The electrode can also be  
3-dimensional surface or object.  
a
Start  
C
Sensitivity is related to electrode  
surface area, orientation with respect  
to the object being sensed, object  
composition, and the ground coupling  
quality of both the sensor circuit and  
the sensed object.  
Done  
x
SNS1  
Charge  
Amp  
If a relatively large electrode surface is  
desired, and if tests show that the  
electrode has more capacitance than  
the QT113 can tolerate, the electrode  
- 2 -  
can be made into a sparse mesh (Figure 1-3) having lower crumpled into a ball. Virtual ground planes are more effective  
Cx than a solid plane. Sensitivity may even remain the same, and can be made smaller if they are physically bonded to  
as the sensor will be operating in a lower region of the gain other surfaces, for example a wall or floor.  
curves.  
1.3.4 FIELD SHAPING  
The electrode can be prevented from sensing in undesired  
1.3.2 KIRCHOFF’S CURRENT LAW  
Like all capacitance sensors, the QT113 relies on Kirchoff’s directions with the assistance of metal shielding connected to  
Current Law (Figure 1-4) to detect the change in capacitance circuit ground (Figure 1-5). For example, on flat surfaces, the  
of the electrode. This law as applied to capacitive sensing field can spread laterally and create a larger touch area than  
requires that the sensor’s field current must complete a loop, desired. To stop field spreading, it is only necessary to  
returning back to its source in order for capacitance to be surround the touch electrode on all sides with a ring of metal  
sensed. Although most designers relate to Kirchoff’s law with connected to circuit ground; the ring can be on the same or  
regard to hardwired circuits, it applies equally to capacitive opposite side from the electrode. The ring will kill field  
field flows. By implication it requires that the signal ground spreading from that point outwards.  
and the target object must both be coupled together in some  
If one side of the panel to which the electrode is fixed has  
manner for a capacitive sensor to operate properly. Note that  
moving traffic near it, these objects can cause inadvertent  
there is no need to provide actual hardwired ground  
detections. This is called ‘walk-by’ and is caused by the fact  
connections; capacitive coupling to ground (Cx1) is always  
that the fields radiate from either surface of the electrode  
sufficient, even if the coupling might seem very tenuous. For  
equally well. Again, shielding in the form of a metal sheet or  
example, powering the sensor via an isolated transformer will  
foil connected to circuit ground will prevent walk-by; putting a  
provide ample ground coupling, since there is capacitance  
small air gap between the grounded shield and the electrode  
between the windings and/or the transformer core, and from  
will keep the value of Cx lower and is encouraged. In the  
the power wiring itself directly to 'local earth'. Even when  
case of the QT113, sensitivity can be high enough  
battery powered, just the physical size of the PCB and the  
(depending on Cx and Cs) that 'walk-by' signals are a  
object into which the electronics is embedded will generally  
concern; if this is a problem, then some form of rear shielding  
be enough to couple a few picofarads back to local earth.  
may be required.  
1.3.3 VIRTUAL CAPACITIVE GROUNDS  
When detecting human contact (e.g. a fingertip), grounding  
1.3.5 SENSITIVITY  
The QT113 can be set for one of 2 gain levels using option  
pin 5 (Table 1-1). This sensitivity change is made by altering  
Figure 1-3 Mesh Electrode Geometry  
the internal numerical threshold level required for a detection.  
Note that sensitivity is also a function of other things: like the  
value of Cs, electrode size, shape, and orientation, the  
composition and aspect of the object to be sensed, the  
thickness and composition of any overlaying panel material,  
and the degree of ground coupling of both sensor and object.  
1.3.5.1 Increasing Sensitivity  
In some cases it may be desirable to increase sensitivity  
further, for example when using the sensor with very thick  
panels having a low dielectric constant.  
Sensitivity can often be increased by using a bigger  
electrode, reducing panel thickness, or altering panel  
composition. Increasing electrode size can have diminishing  
returns, as high values of Cx will reduce sensor gain (Figures  
of the person is never required. The human body naturally  
has several hundred picofarads of ‘free space’ capacitance to  
the local environment (Cx3 in Figure 1-4), which is more than  
two orders of magnitude greater than that required to create  
a return path to the QT113 via earth. The QT113's PCB  
however can be physically quite small, so there may be little  
‘free space’ coupling (Cx1 in Figure 1-4) between it and the  
environment to complete the return path. If the QT113 circuit  
ground cannot be earth grounded by wire, for example via  
the supply connections, then a ‘virtual capacitive ground’ may  
be required to increase return coupling.  
Figure 1-4 Kirchoff's Current Law  
C
X2  
A ‘virtual capacitive ground’ can be created by connecting the  
QT113’s own circuit ground to:  
Sense E lectrode  
(1) A nearby piece of metal or metallized housing;  
(2) A floating conductive ground plane;  
(3) A nail driven into a wall;  
(4) A larger electronic device (to which its output might be  
connected anyway).  
SENSOR  
C
X1  
Free-floating ground planes such as metal foils should  
maximize exposed surface area in a flat plane if possible. A  
square of metal foil will have little effect if it is rolled up or  
C
X3  
Su rro und in g e nviro nm e n t  
- 3 -  
Drift compensation (Figure 2-1) is performed by making the  
reference level track the raw signal at a slow rate, but only  
while there is no detection in effect. The rate of adjustment  
must be performed slowly, otherwise legitimate detections  
could be ignored. The QT113 drift compensates using a  
slew-rate limited change to the reference level; the threshold  
and hysteresis values are slaved to this reference.  
Figure 1-5 Shielding Against Fringe Fields  
Once an object is sensed, the drift compensation mechanism  
ceases since the signal is legitimately high, and therefore  
should not cause the reference level to change.  
The QT113's drift compensation is 'asymmetric': the  
reference level drift-compensates in one direction faster than  
it does in the other. Specifically, it compensates faster for  
decreasing signals than for increasing signals. Increasing  
signals should not be compensated for quickly, since an  
approaching finger could be compensated for partially or  
entirely before even approaching the sense electrode.  
However, an obstruction over the sense pad, for which the  
sensor has already made full allowance for, could suddenly  
be removed leaving the sensor with an artificially elevated  
reference level and thus become insensitive to touch. In this  
latter case, the sensor will compensate for the object's  
removal very quickly, usually in only a few seconds.  
Sense  
wire  
Sense  
wire  
Unshielded  
Electrode  
Shielded  
Electrode  
With large values of Cs and small values of Cx, drift  
compensation will appear to operate more slowly than with  
4-1 to 4-3). The value of Cs also has a dramatic effect on  
sensitivity, and this can be increased in value (up to a limit).  
Also, increasing the electrode's surface area will not  
substantially increase touch sensitivity if its diameter is  
already much larger in surface area than the object being  
detected. The panel or other intervening material can be  
made thinner, but again there are diminishing rewards for  
doing so. Panel material can also be changed to one having  
a higher dielectric constant, which will help propagate the  
field through to the front. Locally adding some conductive  
material to the panel (conductive materials essentially have  
an infinite dielectric constant) will also help; for example,  
adding carbon or metal fibers to a plastic panel will greatly  
increase frontal field strength, even if the fiber density is too  
low to make the plastic bulk-conductive.  
Table 1-1 Gain Setting Strap Options  
Gain  
High - 6 counts  
Low - 12 counts  
Tie Pin 5 to:  
Vdd  
Vss (Gnd)  
the converse. Note that the positive and negative drift  
compensation rates are different.  
2.1.2 THRESHOLD CALCULATION  
Unlike the QT110 device, the internal threshold level is fixed  
at one of two setting as determined by Table 1-1. These  
setting are fixed with respect to the internal reference level,  
which in turn can move in accordance with the drift  
compensation mechanism..  
1.3.5.2 Decreasing Sensitivity  
In some cases the QT113 may be too sensitive, even on low  
gain. In this case gain can be lowered further by a number of  
strategies: making the electrode smaller, making the  
The QT113 employs  
threshold level of 17% of the delta between the reference and  
threshold levels.  
a hysteresis dropout below the  
electrode into  
a
sparse mesh  
using  
a
high  
space-to-conductor ratio (Figure 1-3), or by decreasing Cs.  
2.1.3 MAX ON-DURATION  
If an object or material obstructs the sense pad the signal  
may rise enough to create a detection, preventing further  
2 - QT113 SPECIFICS  
2.1 SIGNAL PROCESSING  
Figure 2-1 Drift Compensation  
The QT113 processes all signals using 16 bit  
math, using a number of algorithms pioneered by  
Quantum. The algorithms are specifically  
designed to provide for high 'survivability' in the  
face of numerous adverse environmental  
Signal  
Hysteresis  
changes.  
Threshold  
Reference  
2.1.1 DRIFT COMPENSATION ALGORITHM  
Signal drift can occur because of changes in Cx  
and Cs over time. It is crucial that drift be  
compensated for, otherwise false detections,  
non-detections, and sensitivity shifts will follow.  
Output  
- 4 -  
operation. To prevent this, the sensor includes a timer which increasing levels of Cs reduce response time. Figure 4-3  
monitors detections. If a detection exceeds the timer setting, shows the typical effects of Cs and Cx on response time.  
the timer causes the sensor to perform a full recalibration  
(when not set to infinite). This is known as the Max  
On-Duration feature.  
2.2 OUTPUT FEATURES  
The QT113 is designed for maximum flexibility and can  
accommodate most popular sensing requirements. These  
are selectable using strap options on pins OPT1 and OPT2.  
All options are shown in Table 2-1.  
After the Max On-Duration interval, the sensor will once again  
function normally, even if partially or fully obstructed, to the  
best of its ability given electrode conditions. There are two  
finite timeout durations available via strap option: 10 and 60  
seconds (Table 2-1).  
2.2.1 DC MODE OUTPUT  
The output of the QT113 can respond in a DC mode, where  
the output is active-low upon detection. The output will  
remain active-low for the duration of the detection, or until the  
Max On-Duration expires (if not infinite), whichever occurs  
first. If a max on-duration timeout occurs first, the sensor  
performs a full recalibration and the output becomes inactive  
until the next detection.  
2.1.4 DETECTION INTEGRATOR  
It is desirable to suppress detections generated by electrical  
noise or from quick brushes with an object. To accomplish  
this, the QT113 incorporates a detect integration counter that  
increments with each detection until a limit is reached, after  
which the output is activated. If no detection is sensed prior  
to the final count, the counter is reset immediately to zero. In  
the QT113, the required count is 3.  
In this mode, three Max On-Duration timeouts are available:  
10 seconds, 60 seconds, and infinite.  
The Detection Integrator can also be viewed as a 'consensus'  
filter, that requires three detections in three successive bursts  
to create an output.  
Table 2-1 Output Mode Strap Options  
Tie  
Pin 3 to:  
Tie  
Pin 4 to:  
Max On-  
Duration  
2.1.5 FORCED SENSOR RECALIBRATION  
The QT113 has no recalibration pin; a forced recalibration is  
accomplished only when the device is powered up. However,  
supply drain is low so it is a simple matter to treat the entire  
IC as a controllable load; simply driving the QT113's Vdd pin  
directly from another logic gate or a microcontroller port  
(Figure 2-2) will serve as both power and 'forced recal'. The  
source resistance of most CMOS gates and microcontrollers  
are low enough to provide direct power without problem. Note  
that most 8051-based micros have only a weak pullup drive  
capability and will require CMOS buffering. 74HC or 74AC  
series gates can directly power the QT113, as can most other  
microcontrollers.  
Vdd  
Vdd  
Gnd  
Gnd  
Vdd  
Gnd  
Gnd  
Vdd  
10s  
60s  
DC Out  
DC Out  
Toggle  
DC Out  
10s  
infinite  
Infinite timeout is useful in applications where a prolonged  
detection can occur and where the output must reflect the  
detection no matter how long. In infinite timeout mode, the  
designer should take care to be sure that drift in Cs, Cx, and  
Vdd do not cause the device to ‘stick on’ inadvertently even  
when the target object is removed from the sense field.  
Option strap configurations are read by the QT113 only on  
powerup. Configurations can only be changed by powering  
the QT113 down and back up again; again, a microcontroller  
can directly alter most of the configurations and cycle power  
to put them in effect.  
2.2.2 TOGGLE MODE OUTPUT  
This makes the sensor respond in an on/off mode like a flip  
flop. It is most useful for controlling power loads, for example  
in kitchen appliances, power tools, light switches, etc.  
2.1.6 RESPONSE TIME  
Max On-Duration in Toggle mode is fixed at 10 seconds.  
When a timeout occurs, the sensor recalibrates but leaves  
the output state unchanged.  
The QT113's response time is highly dependent on burst  
length, which in turn is dependent on Cs and Cx (see Figures  
4-1, 4-2). With increasing Cs, response time slows, while  
2.2.3 HEARTBEAT™ OUTPUT  
The QT113 output has a full-time HeartBeat™ ‘health’  
indicator superimposed on it. This operates by taking 'Out'  
into a 3-state mode for 300µs once after every QT burst. This  
output state can be used to determine that the sensor is  
operating properly, or, it can be ignored using one of several  
simple methods.  
Figure 2-2 Powering From a CMOS Port Pin  
P O RT X .m  
The HeartBeat indicator can be sampled by using a pulldown  
resistor on Out, and feeding the resulting negative-going  
pulse into a counter, flip flop, one-shot, or other circuit. Since  
Out is normally high, a pulldown resistor will create negative  
HeartBeat pulses (Figure 2-3) when the sensor is not  
detecting an object; when detecting an object, the output will  
remain low for the duration of the detection, and no  
HeartBeat pulse will be evident.  
0.01µF  
CMOS  
microcontroller  
V dd  
P O RT X .n  
O UT  
QT110  
If the sensor is wired to a microcontroller as shown in Figure  
2-4, the microcontroller can reconfigure the load resistor to  
either ground or Vcc depending on the output state of the  
QT113, so that the pulses are evident in either state.  
V ss  
- 5 -  
Figure 2-3  
Figure 2-4  
Getting HearBeat pulses with a pull-down resistor  
Using a micro to obtain HB pulses in either output state  
+2.5 to 5  
HeartBeat™ Pulses  
1
PORT_M.x  
2
3
4
7
5
6
OUT  
SNS2  
GAIN  
SNS1  
Vdd  
2
3
4
7
5
6
R
o
OUT  
SNS2  
GAIN  
SNS1  
Ro  
Microcontroller  
OPT1  
OPT2  
OPT1  
OPT2  
PORT_M.y  
Vss  
8
Electromechanical devices like relays will usually ignore this ‘stiction’, the opposite effect, can occur if a load is shed when  
short pulse. The pulse also has too low a duty cycle to visibly Out is active.  
affect LED’s. It can be filtered completely if desired, by  
The output of the QT113 can directly drive a resistively  
adding an RC timeconstant to filter the output, or if interfacing  
limited LED. The LED should be connected with its cathode  
directly and only to a high-impedance CMOS input, by doing  
to the output and its anode towards Vcc, so that it lights when  
nothing or at most adding a small non-critical capacitor from  
the sensor is active. If desired the LED can be connected  
Out to ground (Figure 2-5).  
from Out to ground, and driven on when the sensor is  
inactive.  
The QT113H variant has an active-high output; the heartbeat  
signal of the QT113H works in exactly the same manner.  
The QT113H variant has an active-high output.  
2.2.4 OUTPUT DRIVE  
The QT113’s `output is active low and can sink up to 5mA of  
non-inductive current. If an inductive load is used, such as a  
small relay, the load should be diode clamped to prevent  
damage. When set to operate in a proximity mode (at high  
gain) the current should be limited to 1mA to prevent gain  
shifting side effects from occurring, which happens when the  
load current creates voltage drops on the die and bonding  
wires; these small shifts can materially influence the signal  
level to cause detection instability as described below.  
3 - CIRCUIT GUIDELINES  
3.1 SAMPLE CAPACITOR  
Charge sampler Cs can be virtually any plastic film or  
medium-K ceramic capacitor. The acceptable Cs range is  
from 10nF to 500nF depending on the sensitivity required;  
larger values of Cs demand higher stability to ensure reliable  
sensing. Acceptable capacitor types include polycarbonate,  
PPS film, or NPO/C0G ceramic.  
Care should be taken when the QT113 and the load are both  
powered from the same supply, and the supply is minimally  
regulated. The QT113 derives its internal references from the  
power supply, and sensitivity shifts can occur with changes in  
Vdd, as happens when loads are switched on. This can  
induce detection ‘cycling’, whereby an object is detected, the  
load is turned on, the supply sags, the detection is no longer  
sensed, the load is turned off, the supply rises and the object  
is reacquired, ad infinitum. To prevent this occurrence, the  
output should only be lightly loaded if the device is operated  
from an unregulated supply, e.g. batteries. Detection  
3.2 OPTION STRAPPING  
The option pins Opt1 and Opt2 should never be left floating.  
If they are floated, the device will draw excess power and the  
options will not be properly read on powerup. Intentionally,  
there are no pullup resistors on these lines, since pullup  
resistors add to power drain if tied low.  
The Gain input should be connected to either Vdd or Gnd.  
Tables 1-1 and 2-1 show the option strap configurations  
available.  
Figure 2-5 Eliminating HB Pulses  
3.4 POWER SUPPLY, PCB LAYOUT  
The power supply can range from 2.5 to 5.0 volts. At 3 volts  
current drain averages less than 600µA in most cases, but  
can be higher if Cs is large. Increasing Cx values will actually  
decrease power drain. Operation can be from batteries, but  
be cautious about loads causing supply droop (see Output  
Drive, previous section).  
GATE OR  
MICRO INPUT  
2
3
4
7
5
6
C MO S  
OUT  
SNS2  
GAIN  
SNS1  
Co  
100pF  
OPT1  
OPT2  
As battery voltage sags with use or fluctuates slowly with  
temperature, the QT113 will track and compensate for these  
changes automatically with only minor changes in sensitivity.  
If the power supply is shared with another electronic system,  
care should be taken to assure that the supply is free of  
- 6 -  
Because the charge and transfer times of the QT113  
are relatively long, the circuit can tolerate very large  
values of Re, even to 100k ohms in most cases where  
electrode Cx is small. The added diodes shown  
(1N4150 or equivalent low-C diodes, or a single BAV99  
dual-diode) will shunt the ESD transients away from the  
part, and Re1 will current limit the rest into the QT113's  
own internal clamp diodes. C1 should be around 10µF  
if it is to absorb positive transients from a human body  
model standpoint without rising in value by more than 1  
volt. If desired C1 can be replaced with an appropriate  
Zener diode. Directly placing semiconductor transient  
protection devices, Zeners, or MOV's on the sense lead  
is not advised; these devices have extremely large  
amounts of unstable parasitic C which will swamp the  
QT113 and render it useless.  
Figure 3-1 ESD Suppression Circuit  
+2.5 to 5  
C1  
+
10µF  
R
e2  
1
D
1
2
Vdd  
2
3
4
7
5
6
SENSING  
ELECTRODE  
OUT  
SNS2  
R
R
e1  
e3  
D
OPT1  
OPT2  
GAIN  
SNS1  
C
s
Vss  
8
Re1 should be as large as possible given the load  
value of Cx and the diode capacitances of D1 and D2,  
but Re1 should be low enough to permit at least 6  
timeconstants of RC to occur during the charge and transfer  
phases.  
digital spikes, sags, and surges which can adversely affect  
the QT113. The QT113 will track slow changes in Vdd, but it  
can be affected by rapid voltage steps.  
if desired, the supply can be regulated using a conventional  
low current regulator, for example CMOS regulators that have  
low quiescent currents.  
Re2 functions to isolate the transient from the QT113's Vdd  
pin; values of around 1K ohms are reasonable.  
As with all ESD protection networks, it is crucial that the  
transients be led away from the circuit. PCB ground layout is  
crucial; the ground connections to D1, D2, and C1 should all  
go back to the power supply ground or preferably, if  
available, a chassis ground connected to earth. The currents  
should not be allowed to traverse the area directly under the  
QT113.  
3.5 ESD PROTECTION  
In cases where the electrode is placed behind a dielectric  
panel, the QT113 will usually be adequately protected from  
direct static discharge. However, even with a plastic or glass  
panel, transients can still flow into the electrode via induction,  
or in extreme cases, via dielectric breakdown. Porous  
materials may allow a spark to tunnel right through the  
material; partially conducting materials like 'pink poly' will  
conduct the ESD right to the electrode. Testing is required to  
reveal any problems. The QT113 does have diode protection  
on its terminals which can absorb and protect the device from  
most induced discharges, up to 20mA; the usefulness of the  
internal clamping will depending on the dielectric properties,  
panel thickness, and rise time of the ESD transients.  
If the QT113 is connected to an external circuit via a cable or  
long twisted pair, it is possible for ground-bounce to cause  
damage to the Out pin; even though the transients are led  
away from the QT113 itself, the connected signal or power  
ground line will act as an inductor, causing a high differential  
voltage to build up on the Out wire with respect to ground. If  
this is a possibility, the Out pin should have a resistance Re3  
in series with it to limit current; this resistor should be as  
large as can be tolerated by the load.  
ESD dissipation can be aided further with an added diode  
protection network as shown in Figure 3-1, in extreme cases.  
- 7 -  
4.1 ABSOLUTE MAXIMUM SPECIFICATIONS  
Operating temp . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . as designated by suffix  
Storage temp . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -55OC to +125OC  
VDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.5 to +6.5V  
Max continuous pin current, any control or drive pin . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±20mA  
Short circuit duration to ground, any pin . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . infinite  
Short circuit duration to VDD, any pin . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . infinite  
Voltage forced onto any pin . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.6V to (Vdd + 0.6) Volts  
4.2 RECOMMENDED OPERATING CONDITIONS  
VDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +2.5 to 5.5V  
Short-term supply ripple+noise . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±5mV  
Long-term supply stability . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±100mV  
Cs value . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10nF to 500nF  
Cx value . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0 to 100pF  
4.3 AC SPECIFICATIONS Vdd = 3.0, Ta = recommended operating range, Cs=100nF unless noted  
Parameter  
Description  
Min  
Typ  
Max  
Units  
Notes  
TRC  
TPC  
TPT  
TBS  
TBL  
TR  
Recalibration time  
550  
2
ms  
µs  
Charge duration  
Transfer duration  
Burst spacing interval  
Burst length  
2
µs  
2.1  
0.5  
80  
75  
ms  
ms  
ms  
µs  
Cs = 10nF to 500nF; Cx = 0  
Cs = 10nF to 500nF; Cx = 0  
Cx = 10pF; See Figure 4-3  
Response time  
30  
THB  
Heartbeat pulse width  
300  
4.4 SIGNAL PROCESSING  
Description  
Min  
Typ  
Max  
Units  
Notes  
Threshold differential  
6 or 12  
counts  
%
Option pin selected  
Note 1  
Hysteresis  
17  
Consensus filter length  
3
1,000  
samples  
ms/level  
ms/level  
secs  
Positive drift compensation rate  
Negative drift compensation rate  
Post-detection recalibration timer duration  
Note 1: Percentage of signal threshold  
100  
10, 60, infinite  
Option pin selected  
- 8 -  
4.5 DC SPECIFICATIONS  
Vdd = 3.0V, Cs = 10nF, Cx = 5pF, TA = recommended range, unless otherwise noted  
Parameter  
Description  
Min  
Typ  
Max  
Units  
Notes  
VDD  
IDD  
VDDS  
VIL  
VHL  
VOL  
VOH  
IIL  
Supply voltage  
2.45  
5.25  
V
µA  
V/s  
V
Supply current  
600  
1,500  
Supply turn-on slope  
Low input logic level  
High input logic level  
Low output voltage  
High output voltage  
Input leakage current  
Load capacitance range  
Min shunt resistance  
Acquisition resolution  
Sensitivity range  
100  
2.2  
Required for proper startup  
OPT1, OPT2  
0.8  
0.6  
V
OPT1, OPT2  
V
OUT, 4mA sink  
OUT, 1mA source  
OPT1, OPT2  
Vdd-0.7  
0
V
±1  
µA  
pF  
✡
CX  
100  
IX  
1M  
Resistance from SNS1 to SNS2  
Note 2  
AR  
14  
28  
bits  
fF  
S
1,000  
Note 2: Sensitivity depends on value of Cx and Cs. Refer to Figures 4-1, 4-2.  
Figure 4-2 - Typical Threshold Sensitivity vs. Cx,  
Low Gain, at Selected Values of Cs; Vdd = 3.0  
Figure 4-1 - Typical Threshold Sensitivity vs. Cx,  
High Gain, at Selected Values of Cs; Vdd = 3.0  
10.00  
10.00  
1.00  
1.00  
0.10  
0.01  
10nF  
10nF  
20nF  
20nF  
50nF  
50nF  
100nF  
200nF  
500nF  
100nF  
200nF  
0.10  
500nF  
0.01  
0
10  
20  
30  
40  
0
10  
20  
30  
40  
Cx Load, pF  
Cx Load, pF  
- 9 -  
Chart 4-3 - Typical Response Time vs. Cx;  
Vdd = 3.0  
1000.00  
100.00  
10.00  
10nF  
20nF  
50nF  
100nF  
200nF  
500nF  
1.00  
0
10  
20  
30  
40  
Cx Load  
5 ORDERING INFORMATION  
PART  
TEMP RANGE  
PACKAGE  
MARKING  
QT113-D  
QT113-S  
QT113-IS  
QT113H-D  
QT113H-S  
QT113H-IS  
0 - 70C  
0 - 70C  
-40 - 85C  
0 - 70C  
0 - 70C  
-40 - 85C  
PDIP  
SOIC-8  
SOIC-8  
PDIP  
SOIC-8  
SOIC-8  
QT1 + 13  
QT1 + 3  
QT1 + F  
QT1 + 13H  
QT1 + E  
QT1 + K  
- 10 -  
Package type: 8-pin Dual-In-Line  
Millimeters  
Inches  
Max  
SYMBOL  
Min  
Max  
Notes  
Min  
Notes  
a
A
6.096  
7.62  
7.112  
8.255  
10.922  
7.62  
-
0.24  
0.3  
0.28  
0.325  
0.43  
0.3  
M
m
Q
P
9.017  
7.62  
Typical  
BSC  
0.355  
0.3  
Typical  
BSC  
0.889  
0.254  
0.355  
1.397  
2.489  
3.048  
0.381  
3.048  
-
0.035  
0.01  
0.014  
0.055  
0.098  
0.12  
0.015  
0.12  
-
-
-
-
L
0.559  
1.651  
2.591  
3.81  
-
0.022  
0.065  
0.102  
0.15  
-
L1  
F
Typical  
BSC  
Typical  
BSC  
R
r
S
3.556  
4.064  
7.062  
9.906  
0.381  
0.14  
0.16  
0.3  
S1  
Aa  
x
7.62  
0.3  
8.128  
0.203  
0.32  
0.008  
0.39  
0.015  
Y
Package type: 8-pin SOIC  
Millimeters  
Inches  
Max  
SYMBOL  
Min  
Max  
Notes  
Min  
Notes  
M
W
Aa  
H
h
4.800  
5.816  
3.81  
4.979  
6.198  
3.988  
1.728  
0.762  
1.27  
0.189  
0.229  
0.15  
0.196  
0.244  
0.157  
0.068  
0.01  
0.05  
0.019  
0.04  
0.01  
0.03  
8º  
1.371  
0.101  
1.27  
0.054  
0.004  
0.050  
0.014  
0.02  
D
L
BSC  
BSC  
0.355  
0.508  
0.19  
0.483  
1.016  
0.249  
0.762  
8º  
E
e
0.007  
0.229  
0º  
ß
0.381  
0º  
Ø
- 11 -  
Quantum Research Group Ltd  
©2001QRG Ltd.  
Patented and patents pending  
651 Holiday Drive Bldg. 5 / 300  
Pittsburgh, PA 15220 USA  
Tel: 412-391-7367 Fax: 412-291-1015  
admin@qprox.com  
http://www.qprox.com  
In the United Kingdom  
Enterprise House, Southampton, Hants SO14 3XB  
Tel: +44 (0)23 8045 3934 Fax: +44 (0)23 8045 3939  
This device expressly not for use in any medical or human safety related  
application without the express written consent of an officer of the company.  
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