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QT114-S

型号:

QT114-S

描述:

电荷转移QLEVEL传感器IC[ CHARGE-TRANSFER QLEVEL SENSOR IC ]

品牌:

QUANTUM[ QUANTUM RESEARCH GROUP ]

页数:

12 页

PDF大小:

309 K

QProx™ QT114  
CHARGE-TRANSFER QLEVEL SENSOR IC  
! Limit sensing of almost any fluid or powder  
! 2-Tier level sensor - Hi / Low limits with one probe  
! Only one external part required - a 5¢ capacitor  
! Uses internal probes or external electrodes  
! Active high or active low outputs  
Vcc  
Out1  
Out2  
Filt  
1
2
3
4
8
7
6
5
Gnd  
Sns2  
Sns1  
Pol  
! Slosh filter averages response of moving fluids  
! LED drive capable on both outputs  
! 2.5 to 5V 20µA single supply operation  
! HeartBeat™ health indicator on both outputs  
APPLICATIONS -  
! Process controls  
! Vending machines  
! Automotive fluids  
! Consumer appliances  
! Medical fluid sensing  
! Soil moisture sensing  
DESCRIPTION -  
The QT114 QuickLevel™ charge-transfer (“QT”) sensor IC is specifically designed to detect point level in fluids  
and powders. It will project a sense field through almost any dielectric, like glass, plastic, or ceramic, to sense  
level on the inside of a vessel, from its exterior. It has the unique capability of independently sensing two trip  
points when used with structured electrodes having two tiers.  
The QT114 does not have sensing timeouts, drift compensation, or other functions which would interfere with  
level sensing. Its threshold levels are fixed, and the amount of signal required to exceed a threshold is dependent  
on circuit gain and electrode size and loading, all of which are under the control of the designer.  
The QT114 requires only a single inexpensive capacitor in order to function. One or two LEDs can also be added  
to provide a visual sensing indication.  
Power consumption is under 20mA in most applications, allowing operation from Lithium cells for many years. In  
most cases the power supply needs only minimal regulation.  
The QT114 employs numerous signal acquisition and processing techniques pioneered by Quantum. No external  
switches, opamps, or other analog components aside from CS are required.  
A unique feature is the 'slosh filter', a detection integrator which averages detections over a rolling 15 second  
interval before activating or deactivating the OUT pins. This filter allows use of the QT114 with violently moving  
fluids, for example in a moving vehicle, that would otherwise cause the outputs to flicker between two states.  
The device also includes selectable output polarity, allowing both output lines to be made either active-high or  
active-low. It also includes the Quantum-pioneered HeartBeat™ signal, allowing a host controller to monitor the  
health of the QT114 continuously if desired. By using the charge transfer principle, the IC delivers a level of  
performance clearly superior to older technologies. It is specifically designed to replace electromechanical  
devices like float switches, thermistors, and conductance probes.  
AVAILABLE OPTIONS  
TA  
SOIC  
8-PIN DIP  
QT114-D  
-
00C to +700C  
-400C to +850C  
QT114-S  
QT114-IS  
Quantum Research Group Ltd  
Copyright © 1999 Quantum Research Group Ltd  
R1.03  
The QT114 is a digital burst mode charge-transfer (QT)  
sensor designed specifically for point level sensing; it  
includes all hardware and signal processing functions  
necessary to provide stable level sensing under a wide  
variety of changing conditions. Only a single external  
capacitor is required for operation.  
Figure 1-1 shows a basic QT114 circuit using the device,  
with conventional OUT drives and power supply connections.  
The sensing electrode can be connected to a single-tier or  
2-tier electrode as required.  
Calibration is done by design, through adjustment of the  
electrode sizes and the Cs capacitor. Only under rare  
situations do QT114 circuits require calibration on an  
individual basis, and the circuit can make provision for that.  
To 10x Scope Probe  
Vcc  
1
2MΩ  
(optional)  
2
3
4
7
6
OUT1 SNS2  
OUT2 SNS1  
OUT 1  
OUT 2  
To Electrode(s)  
C
s
1M  
multi-turn  
pot (optional)  
5
FILT  
POL  
Gnd  
8
Vdd  
Vdd  
FILTER  
POLARITY  
POL: 1 = Active High  
FILT: 1 = Slosh Filter  
1 - SIGNAL ACQUISITION  
Figure 1-1 Standard mode options  
The QT114 employs a short, low duty cycle burst of  
charge-transfer cycles to acquire its signal. Burst mode  
permits power consumption in the low microamp range,  
dramatically reduces RF emissions, lowers susceptibility to  
EMI, and yet permits excellent response time. Internally the  
signals are digitally processed to generate the required  
output signals.  
It is not necessary to use both detection threshold points; if  
only single point sensing is desired, only the lower threshold  
and OUT1 can be used, while ignoring OUT2.  
Two option pins allow the selection of output polarity and the  
insertion of a 'slosh filter' before the OUT pins, as shown in  
Figure 1-1.  
The QT switches and charge measurement hardware  
functions are all internal to the QT114 (Figure 1-2). A 14-bit  
single-slope switched capacitor ADC includes both the  
required QT charge and transfer switches in a configuration  
that provides direct ADC conversion. The burst length is  
inversely proportional to the rate of charge buildup on Cs,  
which in turn depends on the values of Cs, Cx, and Vcc. Vcc  
is used as the charge reference voltage. Larger values of Cx  
cause the charge transferred into Cs to accumulate more  
rapidly. The trip points of the sensor can be changed by  
altering Cs and Cx, the load capacitance. As a result, the  
values of Cs, Cx, and Vcc should be fairly stable over the  
expected operating temperature range.  
Two fixed thresholds are used, one for low fluid level and the  
other for high level; adjusting Cs and Cx to allow these to trip  
at appropriate points is required by design, and if required  
may be trimmed by an adjustment. Figure 1-1 shows the  
optional potentiometer which can be used to fine-tune the  
placement of these threshold points relative to the signal.  
1.1 ELECTRODE DRIVE  
The internal ADC treats Cs as a floating transfer capacitor;  
as a direct result, the sense electrode can be connected to  
either SNS1 or SNS2 with no performance difference. The  
polarity of the charge buildup across Cs during a burst is the  
same in either case. Cs must be of within a certain range for  
proper operation.  
It is possible to connect separate Cx and Cx’ loads to SNS1  
and SNS2 simultaneously, although the result is no different  
than if the loads were connected together at SNS2 (or  
SNS1). It is important to limit the amount of stray  
capacitance on both terminals, especially if the load Cx is  
already large, for example by minimizing trace lengths and  
widths so as not to exceed the Cx load specification and to  
allow for a larger sensing electrode size if so desired.  
The PCB traces, wiring, and any components associated  
with or in contact with SNS1 and SNS2 will become  
proximity sensitive and should be treated with caution.  
1.2 THRESHOLD POINTS  
The QT114 employs twin threshold points set at both  
250 (for T1) and 150 counts (for T2) of acquisition  
ELECTRO DE  
signal. The signal travels in an inverse direction:  
increasing amounts of Cx reduce the signal level; the  
baseline ('dry') signal should lie at 300 counts or  
more under most conditions. Calibration details are  
discussed fully in Section 3.2.  
Result  
SNS2  
Cs  
Start  
Cx  
Done  
2 ELECTRODE DESIGN  
SNS1  
The QT114 is designed to operate with a 'plateau'  
sensor, having a substantial surface area at each  
desired trip point, to create a capacitive 'step'.  
As Figure 2-1 shows, a vertical strip sensor on the  
outside of a container (or a vertical, insulated rod in  
the fluid) will generate a long sloping signal. The  
desired trip point 'T' is subject to a great deal of  
variation in location if the sensing signal drifts much,  
C harge  
Amp  
Figure 1-2 Internal Switching & Timing  
- 2 -  
for example due to changes in Cs or Cx over the operating  
temperature range.  
Signal  
Figure 2-2 shows the response from a horizontal strip of  
the same surface area; the signal exhibits a very rapid rise  
in signal between points l1 and l2. Variations in circuit  
gain or signal drift have much less of an effect on the trip  
point with this orientation.  
l2  
T1  
In some cases (thin walled vessels for example) it may be  
sufficient to have a small round or square electrode patch  
on the exterior.  
Figure 2-3 shows the response from a twin-level external  
electrode set. The use of two horizontal electrode planes  
or tiers creates well-defined trip points that can be used to  
sense both 'low' and 'high' levels. A crossing of threshold  
T1 will be reflected in the OUT1 signal, while T2 will be  
reflected on OUT2.  
T1  
l1  
Level  
l2  
l1  
Figure 2-1 Signal vs. Level for an External Vertical Strip  
Signal  
2.1 EXTERNAL ELECTRODES  
External electrodes should be electrically conductive;  
metal foils and conductive carbon are both possible. Care  
should be taken that other objects or people near the  
vessel will not touch the electrode; in some cases  
shielding around the electrode with grounded metal will be  
required to prevent disturbances. If used, the shield  
element should be spaced apart from the electrode by an  
air gap or a low-density foam to reduce Cx loading.  
l2  
T1  
l1  
T1  
Level  
l1  
l2  
The required surface area of the external electrode will  
depend on the amount of signal needed to bracket the  
detection threshold, which in turn will depend in part on Cs  
and stray Cx. External electrodes sensing through thick  
walls and/or sensing low permittivity fluids will require  
larger surface areas than those sensing water through thin  
plastic, for example. External electrodes are more likely to  
require potentiometer trimming to achieve reliable  
operation (Figure 1-1, also Section 3.2).  
Figure 2-2 Signal vs. Level for an External Horizontal Strip  
Signal  
T2  
l4  
T2  
T1  
l3  
l1  
Note that external electrodes used with conductive  
solutions (i.e. aqueous liquids) do not measure the  
permittivity of the fluid: they actually measure the  
permittivity of the vessel wall, between 2 plates: the  
electrode (plate 1) and the fluid (plate 2, effectively a  
variable-area ground plate): if the fluid were to be replaced  
with mercury the signal would be unchanged. A 20%  
thickness variation in the vessel wall will therefore  
T1  
l2  
Level  
l3 l4  
l1  
l2  
Figure 2-3 Signal vs. Level for Twin Horizontal Strips  
introduce about  
a
20% variation in the resulting  
2.2.1 DISC PROBES  
capacitance; if the vessel wall cannot be controlled  
accurately enough in production, serious sensing errors may  
occur.  
The simplest internal geometry is probably a disc probe  
(Figure 2-4), having at least one planar surface ('tier')  
parallel to the fluid surface. The sensing error can be  
minimized by making the tier thin, so that the signal  
transitions abruptly higher (see Figure 2-2) as the fluid  
covers the tier.  
When external electrodes are used to sense non-aqueous  
substances (like oils or gasoline), the vessel wall dielectric  
becomes a lessor contributor to the overall signal, which is  
then heavily dominated by the permittivity of the fluid. The  
lower the permittivity of the fluid the greater its dominance.  
A notable difficulty with disc probes is the task of insulating  
them with a uniform, repeatable thickness of insulation.  
2.2 INTERNAL PROBES  
2.2.2 SPIRAL WIRE PROBES  
When used with aqueous fluids or other electrically  
conducting liquids, internal probes should be insulated with a  
plastic layer. See also Section 2.1 for a discussion of  
electrodes when used with conductive fluids. Aqueous  
probes should be 100% insulated, even on the cut end of a  
wire probe. The slightest pinhole of exposed metal anywhere  
on an immersed part of the probe will immediately convert  
the probe into a bare-metal probe (see Section 2.2.5).  
A spiral solid-wire probe is simple to construct (Figure 2-5),  
and has the advantage of being pre-insulated in a wide  
choice of plastics from inexpensive PVC to PTFE. These  
probe types provide a large step-function of capacitance  
localized at the desired trip point, and are easy to form.  
Spiral wire probes are most effective in water-based fluids;  
they are not as effective in oils and other nonconductive  
substances.  
Numerous types of internal point-level probes are possible.  
- 3 -  
Figure 2-4 Single Level Internal Planar Probe  
Figure 2-5 Single Level Internal Spiral Wire Probe  
T2  
T2  
Figure 2-6 Twin-Level Internal Planar Probe  
Figure 2-7 Twin-Level Internal Spiral Wire Probe  
Spiral wire probes have the disadvantage of not being as fluid to fill and drain the cavity without trapping air bubbles  
rugged as a solid disc probe.  
inside. The outer cylinder can also be made of a wire mesh.  
The outer cylinder does not have to be coated in plastic,  
even when used with water-based fluids. When used with  
oils, the inner rod does not require insulation either.  
2.2.3 SIDE-ENTRY PROBES  
Another type is a side-entry probe (Figure 2-8), which  
requires an entry point into the vessel wall, but may have the  
advantage of accessibility in certain cases. These can be  
made of simple metal rod, insulated in almost any plastic if  
required.  
2.2.5 BARE METAL PROBES  
Bare metal internal probes can be used, for example with  
nonconductive fluids like oils, without difficulty. This applies  
to all probe types described above.  
2.2.4 COAXIAL PROBES  
Another type of internal probe is the coaxial probe (Figure  
2-10); these are most useful with oils or similar fluids having  
a low dielectric constant; the inner rod is connected to the  
signal connection, and together with the outer grounded  
cylinder forms a capacitor whose dielectric is either air or oil.  
Keeping the gap between rod and cylinder to a minimum  
increases the 'gain' of the electrode.  
Bare probes can also be used with aqueous fluids, but in  
these cases a 1,000pF (1nF) ceramic NPO capacitor should  
be inserted between the probe and the QT114 to block DC  
current flows.  
A bare internal probe used with conductive fluids and an  
in-line blocking capacitor will generate a huge, robust  
capacitive response that will not readily permit the use of a  
2-level probe due to signal saturation. Even the slightest  
amount of bare metal exposed to the fluid will usually  
generate an immediate, large response with aqueous fluids.  
Coaxial probes are more expensive to make, and can have  
problems with vibration if they are not constructed robustly.  
The outer cylinder should be perforated at key spots to allow  
- 4 -  
T1  
Figure 2-9 Twin-Level Internal Horizontal Probes  
Figure 2-8 Single Internal Horizontal Probe  
T2  
Figure 2-10 Coaxial Probe For Non-Aqueous Fluids  
Figure 2-11 Twin-Level Coaxial Probes For  
Non-Aqueous Fluids  
container, electrically coupled to the fluid mass below, will  
create a substantial capacitive response. Internal probes are  
much more resistant to this effect since the fluid surface is  
guaranteed to become mechanically disconnected from the  
probe when the level drops. Coating the inner vessel surface  
with a smooth plastic of polyethylene or PTFE often has a  
very beneficial effect on this phenomenon.  
2.2.6 SCALE BUILDUP  
Scale buildup on internal probes, bare or insulated, is not  
generally a problem since the sensor is still measuring  
capacitance, not conductance, and  
a
reduction in  
conductivity around the probe will have minimal or no effect.  
Probe designs should be tested for this to be certain in all  
specific cases.  
A legitimate concern with bare metal probes is the buildup of  
scale or other deposits at the entry point of the probe into the  
vessel. Such deposits may create a conductive surface path  
(especially if the vessel is made of metal) that may lead to  
false-positive trips. If the shank of the probe at the entry  
point is insulated enough so that conductive bridging cannot  
occur, this problem should be alleviated.  
2.3 SINGLE LEVEL SENSING  
When sensing for a single trip point, the single electrode can  
be a simple horizontal strip on the outside of a nonmetallic  
vessel (Figure 2-2), or an internal probe having a substantial  
horizontal 'plateau' at the trip point (Figures 2-4, 2-5, 2-8,  
2-10). When the strip or plateau is ‘covered’ with fluid the IC  
will detect on at least the OUT1 line; OUT2 can be ignored.  
2.2.7 VISCOUS, CONDUCTIVE FILMS  
The trip point ideally occurs at the centerline of the internal  
probe or external electrode; this can be trimmed with a  
potentiometer if necessary (see Section 3.2). Making the  
electrode narrow and long (horizontally) will help keep the  
trip point localized within a narrow band.  
Highly viscous fluids, or those having a high surface tension,  
and having substantial conductivity can fool some electrode  
designs into thinking that there is fluid present when there is  
not. This is a particular problem with external electrodes,  
where the residual films of certain types of fluids inside the  
- 5 -  
2.4 DUAL LEVEL SENSING  
3 - PROCESSING &  
CIRCUITRY  
When two trip levels are desired, for  
example for high-low limit sensing, the  
electrode or probe set should have two  
3.1 SLOSH FILTER  
distinct tiers.  
A typical twin external  
It is desirable to suppress rapid, multiple  
detections of fluid level generated by the  
surface movement of the fluid, for  
electrode is shown in Figure 2-3 (they are  
connected together to the sense line);  
typical internal twin electrodes are shown  
in Figures 2-6, 2-7, 2-9, and 2-11. The  
response of a properly constructed 2-tier  
probe is shown in Figure 2-3.  
example in  
a
moving vehicle. To  
accomplish this, the QT114 incorporates a  
detection  
integration  
counter  
that  
increments with each detection until a limit  
is reached, after which point one of the  
Dual level electrodes should have an  
approximately 3:1 surface area ratio or  
more from T2 to T1; that is, the surface  
area at T2 should be at least 3x the  
surface area of the electrode at T1. There  
is no penalty for making T2 excessively  
large. The high ratio is required to  
overcome the QT114's decreasing gain  
with increasing Cx load (Figures 4-1, 4-2).  
With internal dual-level probes where T1  
and T2 are substantially separated, the  
intervening connection between the two  
levels should be more thickly insulated, for  
example with a thick plastic spacer, and  
OUT lines is activated. If during  
a
detection ‘event’ the fluid level falls below  
the electrode level (signal rises above a 'T'  
point in signal counts), the counter  
decrements back towards zero. Over a  
long interval the up and down counts will  
tend towards either zero or the limit, with  
the result being a statistical function of the  
number of detections vs. non-detections. If  
on average there are more detections than  
non-detections, the counter will eventually  
make its way to the limit value and an  
OUT line will activate.  
Figure 2-12 A 2-tier spiral wire  
probe with ground rod  
Once a detection has been established,  
the counter must find its way back to zero before the affected  
OUT line goes inactive, via the same process. Although the  
counter has a nominal reaction time of 15 seconds, in some  
cases it may take several minutes before the outcome is  
resolved depending on the violence of the fluid surface. If the  
fluid surface is stable however, it will only require 15  
seconds to change the state of an OUT line.  
Both OUT1 and OUT2 have their own independent slosh  
filters. Both are enabled or disabled in unison by strap  
option, pin 4, 'FILT' as follows:  
any remaining internal gap inside the spacer should be filled  
with silicone sealant or epoxy. This will help to prevent the  
signal from rising much between the two levels, thus  
preserving a crisp bi-level response like that shown in Figure  
2-3.  
2.5 GROUNDING CONSIDERATIONS  
In all cases ground reference coupling to the fluid must be  
made. In aqueous fluids, this can simply mean connecting  
the metal vessel to circuit ground, or inserting a bare metal  
element into the bottom of a plastic or glass vessel. The  
degree of galvanic contact is not critical, so scale and  
corrosion on the ground electrode are not of great concern  
especially if the 'connection' to the fluid is substantial  
enough.  
FILT = Gnd  
Slosh filter off  
FILT = Vcc  
Slosh filter on  
FILT strapping can be changed 'on the fly'.  
If direct electrical contact to the fluid is not possible, a large  
piece of external metal can be bonded to the outside of the  
vessel and grounded. Once this is done, the signal should be  
monitored while the vessel is touched by hand; if the  
grounding is sufficient, the signal will not move or will move  
only slightly.  
Very large vessels, even if not grounded, often do not require  
additional provision for grounding since the bottom surface  
area and free-space capacitance of the tank may be  
sufficient for ground return coupling.  
In some cases (windshield washer tanks on cars for  
example) there will exist a water path to a chassis-grounded  
fitting somewhere downstream of the tank, or the water path  
may be labyrinthine enough to provide enough capacitive  
coupling to the grounded chassis even if it does not make  
galvanic contact. In these cases no further provision for fluid  
grounding is required. Simple experimentation will easily  
determine whether the existing amount of parasitic coupling  
to ground is enough to do the job.  
3.2 CALIBRATION  
Both the T1 and T2 trip point values are hardwired internally  
as functions of counts of burst length. Sensitivity can be  
altered relative to these trip points by altering electrode size,  
geometry, degree of coupling to the fluid, and the value of  
Cs. Selecting an appropriate value of Cs for a given  
electrode geometry is essential for solid detection stability.  
The QT114 employs dual threshold points set at 250 and  
150 counts of acquisition signal. The signal travels in a  
reverse direction: increasing Cx reduces the signal counts;  
as a result, 250 counts of signal corresponds to the most  
sensitive or ‘lower’ setting (T1), and 150 the least sensitive  
'upper' setting (T2).  
The baseline signal count when the electrodes are 'dry'  
should begin at over 300 counts or more if possible. With a  
small, weakly coupled electrode the baseline signal can be  
trimmed to be closer to the 250 mark with a potentiometer to  
provide a higher apparent gain by closing the gap between  
the baseline and T1 (see below). The spread between T2  
and T1 is fixed and cannot be separately trimmed.  
In the case of coaxial probes, the ground connection is  
inherent in the outer cylinder and no further ground  
connection is required.  
Increasing Cs will increase the baseline counts, while  
increasing Cx will decrease it. When optimally tuned, each  
threshold point will be symmetrically bracketed by signal  
- 6 -  
swing, with an intermediate count at about 200 between the The OUT lines can sink up to 5mA of non-inductive current.  
two. Thus, the lower electrode level should cause a signal If an inductive load is used, like a small relay, the load  
swing that (when 'dry') starts at 300 or more and when should be diode clamped to prevent device damage.  
covered ends at about 200. The upper electrode when  
POL strapping can be changed 'on the fly'.  
covered should generate a signal level of 100 or less.  
Cycling and Stiction: Care should be taken when the QT114  
There is a hysteresis of 3 counts around both T1 and T2.  
and the loads are powered from the same supply, and the  
The signal can be viewed for setup purposes with an supply is minimally regulated. The QT114 derives its internal  
oscilloscope via a 10x or FET probe connected to a 2M ohm references from the power supply, and sensitivity shifts can  
resistor as shown in Figure 1-1; the resistor is required to occur with changes in Vcc, as happens when loads are  
reduce the loading effect of the scope probe capacitance. switched on. This can induce detection ‘cycling’, whereby a  
When viewed this way the signal will appear as a declining trip point is crossed, the load is turned on, the supply sags,  
slope (Figure 3-1). The duration of the slope corresponds to the trip is no longer sensed, the load is turned off, the supply  
the burst length: each count of burst takes approximately 7 rises and the trip point is reacquired, ad infinitum. To prevent  
microseconds on average. The ‘low level’ threshold at 250 this occurrence, the outputs should only be lightly loaded if  
counts is at 1750 microseconds from the start of the the device is operated from a poorly regulated supply.  
waveform, while the 150 count ‘upper’ threshold is at about Detection ‘stiction’, the opposite effect, can occur if a load is  
1050 microseconds from the start, at 3 volts Vcc. These trip shed when an Out line becomes active.  
points can be easily observed by monitoring the OUT lines  
3.3.2 HEARTBEAT™ OUTPUT  
while watching the signal on a scope, by increasing Cx  
loading until each OUT line activates in turn. FILT should be  
off to speed up response during testing.  
Both OUT lines have a full-time HeartBeat™ ‘health’  
indicator superimposed on them. These operate by taking  
both OUT pins into a 3-state mode for 350µs once before  
every QT measurement burst. This state can be used to  
determine that the sensor is operating properly, or, it can be  
ignored using one of several simple methods.  
The QT114's internal clock is dependent on Vcc; as a result,  
the threshold points in terms of delay time from the start of  
the burst are also substantially dependent on Vcc, but they  
are always fixed in terms of signal counts. A regulated power  
supply is strongly advised to maintain the proper calibration  
points.  
If active-low polarity is selected, the HeartBeat indicator can  
be sampled by using a pulldown resistor on one or both OUT  
lines, and feeding the resulting negative-going pulse(s) into a  
counter, flip flop, one-shot, or other circuit (Figure 3-2). In  
this configuration, the pulldown resistor will create  
negative-going HeartBeat pulses when the sensor is not  
detecting fluid; when detecting fluid, the OUT line will remain  
low for the duration of the detection, and no pulse will be  
evident. Conversely, a pull-up resistor will show HeartBeat  
pulses when the line is low (detecting).  
If active-high OUT polarity is selected, the pulses will only  
appear if there is a pull-up resistor in place and the fluid is  
not present (no detection, low output), or, if there is a  
pull-down resistor and the output is active (high output).  
Potentiometer adjustment:  
The external potentiometer  
shown in Figure 1-1 is optional and in most cases not  
required. In situations where the electrode pickup signal is  
weak, trimming may be necessary on a production basis to  
make the device sensitive enough. Trimming affects the  
baseline reference of the signal, and thus effects the amount  
of change in the signal required to cause a threshold  
crossing.  
Potentiometer trimming is not a substitute for a good choice  
of Cs. In low signal situations Cs should still be determined  
by design to allow the baseline signal to be just beyond T1  
as viewed on a scope. The trimmer should then be added  
and the baseline adjusted to the necessary final resting  
point.  
The trimmer should never be adjusted so that the resistance  
from ground to SNS1 or SNS2 is less than 200K ohms. If the  
resistance is less than this amount, the gain of the circuit will  
be appreciably reduced and it may stop functioning  
altogether. A 200K resistor from the wiper to ground can  
be added to limit trim current at the extremes of wiper  
travel.  
If the sensor is wired to a microprocessor as shown in Figure  
3-3, the microprocessor can reconfigure the load resistor to  
either ground or Vcc depending on the output state of the  
QT114, so that the pulses are evident in either state with  
either POL setting.  
3.3 INTERFACING  
3.3.1 OUT LINES AND POLARITY SELECTION  
The QT114 has two OUT pins, OUT1 and OUT2, which  
correspond to the crossings of signal at T1 and T2  
respectively. Each output will become active after the  
threshold is crossed, and after the slosh filter (if enabled)  
has settled to its final state. The polarity of the OUT lines  
is determined by pin 5, 'POL', as follows:  
POL = Gnd  
Outputs active low  
POL = Vcc  
Outputs active high  
There is no timeout on these outputs; the OUT lines will  
remain active for as long as the thresholds are crossed.  
Figure 3-1 Burst Waveform at 2M Pickoff Resistor  
- 7 -  
Figure 3-2  
Figure 3-3  
Getting HeartBeat pulses with a pull-down resistor  
Using a micro to obtain HB pulses in either output state  
HeartBeat™ Pulses  
2
7
6
5
PORT_M.1  
2
3
4
7
6
5
OUT1  
OUT2  
FILT  
SNS2  
SNS1  
POL  
OUT1  
OUT2  
FILT  
SNS2  
SNS1  
POL  
R
R
1
2
PORT_M.2  
PORT_M.3  
Ro  
3
4
Microprocessor  
PORT_M.4  
Ro  
Electromechanical devices will ignore this short pulse. The semiconductor transient protection devices or MOV's on the  
pulse also has too low a duty cycle to visibly affect LED’s. It sense lead is not advised; these devices have extremely  
can be filtered completely if desired, by adding an RC large amounts of parasitic C which will swamp the sensor.  
timeconstant to filter the output, or if interfacing directly and  
Re2 functions to isolate the transient from the QT110's Vcc  
only to a high-impedance CMOS input, by doing nothing or  
pin; values of around 1K ohms are reasonable.  
at most adding a small non-critical capacitor from each used  
OUT line to ground (Figure 3-4).  
As with all ESD protection networks, it is important that the  
transients be led away from the circuit. PCB ground layout is  
crucial; the ground connections to the diodes and C1 should  
all go back to the power supply ground or preferably, if  
available, a chassis ground connected to earth. The currents  
should not be allowed to traverse the area directly under the  
QT114.  
3.4 ESD PROTECTION  
In some installations the QT114 will be protected from direct  
static discharge by the insulation of the electrode and the  
GATE OR  
MICRO INPUT  
If the QT114 is connected to an external circuit via a long  
cable, it is possible for ground-bounce to cause damage to  
the OUT pins; even though the transients are led away from  
the QT114 itself, the connected signal or power ground line  
will act as an inductor, causing a high differential voltage to  
build up on the OUT wires with respect to ground. If this is a  
possibility, the OUT pins should have a resistance in series  
with them on the sensor PCB to limit current; this resistor  
should be as large as can be tolerated by the load.  
2
3
4
7
6
5
CMOS  
OUT1  
OUT2  
FILT  
SNS2  
SNS1  
POL  
Co  
100pF  
100pF  
CMOS  
Co  
3.5 SAMPLE CAPACITOR  
Figure 3-4 Eliminating HB Pulses  
Charge sampler Cs should be a stable grade of capacitor,  
like PPS film, NPO ceramic, or polycarbonate. The  
acceptable Cs range is anywhere from 10nF to 100nF  
(0.1uF) and its required value will depend on load Cx. In  
some cases, to achieve the 'right' value, two or more  
capacitors may need to be wired in parallel.  
fact that the probe may not be accessible to human contact.  
However, even with probe insulation, transients can still flow  
into the electrode via induction, or in extreme cases, via  
dielectric breakdown. Some moving fluids (like oils) and  
powders can build up a substantial triboelectric charge  
directly on the probe surface.  
The QT114 does have diode protection on its terminals  
which can absorb and protect the device from most induced  
discharges, up to 20mA; the usefulness of the internal  
clamping will depending on the probe insulation's dielectric  
properties, thickness, and the rise time of the transients.  
ESD dissipation can be aided further with an added diode  
protection network as shown in Figure 3-5. Because the  
charge and transfer times of the QT114 are relatively long,  
the circuit can tolerate very large values of Re1, as much as  
50k ohms in most cases without affecting gain. The added  
diodes shown (1N4150, BAV99 or equivalent low-C diodes)  
will shunt the ESD transients away from the part, and Re1  
will current-limit the rest into the QT110's own internal clamp  
diodes. C1 should be around 10µF if it is to absorb positive  
transients from a human body model standpoint without  
rising in value by more than 1 volt. If desired C1 can be  
replaced with an appropriate zener diode. Directly placing  
Vcc  
C1  
10F  
Re  
Re  
2
1
1
To Electrodes  
2
3
4
7
6
5
OUT1  
OUT2  
FILT  
SNS2  
SNS1  
CS  
POL  
Gnd  
8
Figure 3-5 ESD Protection Network  
- 8 -  
The value of Cs controls the calibration point (Section 3.2)  
and its selection should not be taken lightly.  
3.7 PC BOARD LAYOUT  
There are only a few important issues for the PCB layout.  
For RF susceptibility reasons it should be compact, and if  
possible use SMT components and a ground plane (Section  
3.8). Lines for SNS1 and SNS2 should be short and not run  
directly over the ground plane to reduce Cx loading, which  
adversely affects sensitivity (Section 3.2). ESD issues should  
be taken into account (Section 3.4). The board should not be  
located in a place where there are wild temperature swings  
which can cause excessive drift in Cs. The voltage regulator  
should be located nearby and should only be shared with  
other circuits that do not induce supply sags or spikes  
(Section 3.6).  
3.6 POWER SUPPLY  
The power supply can range from 2.5 to 5.0 volts. At 3 volts  
current drain averages less than 20µA in most cases.  
Operation can be from batteries, especially stable Lithium  
cells, but be cautious about loads causing supply droop  
(Section 3.3.1).  
If the power supply is shared with another electronic system,  
care should be taken to assure that the supply is free of  
digital spikes, sags, and surges which can adversely affect  
the QT114.  
If desired, the supply can be regulated using a conventional  
low current regulator, for example CMOS regulators that  
have nanoamp quiescent currents. The voltage regulator  
should not have a minimum load specification, which almost  
certainly will be violated by the QT114's low current  
requirement.  
Since the QT114 operates in a burst mode, almost all the  
power is consumed during the course of each burst. During  
the time between bursts the sensor is quiescent.  
3.8 RFI / EMI ISSUES  
3.8.1 SUSCEPTIBILITY  
The QT114 is remarkably resistant to RF fields. With enough  
field strength at frequencies above 100MHz, internal  
protection diode conduction at the SNS1 and SNS2 pins can  
occur and destroy the charge-transfer process, causing false  
detections or desensitization, or alternating cycles of both.  
Susceptibility can be dramatically reduced by adding a  
resistor in series with the Sense line, between 2K to 60K  
ohms depending on load Cx. This has the effect of creating a  
natural low-pass filter in conjunction with the Cs capacitor to  
filter out external RF components. If an ESD network is used  
(Figure 3-5), the added resistor should be placed between  
the clamp diodes and the sense probe, and Re1 should be  
made very small, 1K ohms or less, or even eliminated. With  
a 50pF load the added resistance should be no greater than  
about 5.6K ohms, while at 10pF it can be as high as 27K;  
the value should be chosen to allow at least 7 RC  
timeconstants of settling with a 2µs charge time for efficient,  
stable operation. 5% tolerance resistors can be used.  
3.6.1 MEASURING SUPPLY CURRENT  
Measuring average power consumption is a fairly difficult  
task, due to the burst nature of the QT110's operation. Even  
a good quality RMS DMM will have difficulty tracking the low  
burst rate.  
The simplest method for measuring average current is to  
replace the power supply with a large value low-leakage  
electrolytic capacitor, for example 2,700µF. 'Soak' the  
capacitor by connecting it to a bench supply at the desired  
operating voltage for 24 hours to form the electrolyte and  
reduce leakage to a minimum. Connect the capacitor to the  
QT114 circuit at T=0, making sure there will be no detections  
during the measurement interval and no loads on the OUT  
pins; at T=30 seconds measure the capacitor's voltage with  
a DMM. Repeat the test without a load to measure the  
capacitor's internal leakage, and subtract the internal  
leakage result from the voltage droop measured during the  
QT114 load test. Be sure the DMM is connected only at the  
end of each test, to prevent the DMM's own impedance from  
contributing to the capacitor's discharge.  
A great number of susceptibility problems can be traced to  
RF fields coupling directly to components on the PCB.  
Therefore a shielded, grounded housing is recommended to  
reduce susceptibility. The use of SMT circuitry is also highly  
recommended; physically reducing lead lengths of the wiring  
traces and pins, along with a poured-copper ground plane,  
will dramatically reduce the coupling of external RF fields.  
3.8.2 RF EMISSIONS  
RF emissions are extremely weak, as the charge-transfer  
pulse frequency is only about 170kHz and the bursts are  
sparsely spaced, so that the average spectral power density  
is extremely low. The addition of a series resistor for EMI  
reasons (above) will dramatically reduce edge rise and fall  
times, resulting in an even greater reduction in emitted RF  
energy.  
Supply drain can be calculated from the adjusted voltage  
droop using the basic charge equation:  
VC  
i =  
t
where C is the supply capacitor's value, t is the elapsed  
measurement time in seconds, and DV is the adjusted  
voltage droop on C.  
- 9 -  
4.1 ABSOLUTE MAXIMUM SPECIFICATIONS  
Operating temp . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . as designated by suffix  
Storage temp . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -55OC to +125OC  
VCC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.5 to +6.5V  
Max continuous pin current, any control or drive pin . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±20mA  
Short circuit duration to ground, any pin . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . infinite  
Short circuit duration to VCC, any pin . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . infinite  
Voltage forced onto any pin . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . -0.6V to (Vcc + 0.6) Volts  
4.2 RECOMMENDED OPERATING CONDITIONS  
VCC . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +2.5 to 5.25V  
Supply ripple+noise . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20mV p-p max  
Load capacitance . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0 to 50pF  
Cs value . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10nF to 100nF  
4.3 AC SPECIFICATIONS Vcc = 3.0, Ta = recommended operating range  
Parameter  
Notes  
Description  
Min  
Typ  
Max  
Units  
TPC  
TPT  
TBS  
TBL  
NLC  
TR  
Charge duration  
Transfer duration  
Burst spacing interval  
Burst length, time  
Maximum burst length counts  
Response time  
2
4
75  
µs  
µs  
ms  
ms  
counts  
ms  
µs  
0
6
3.5  
14  
500  
80  
Slosh filter disabled  
TQ  
QT pulse spacing  
TR  
TF  
Pulse edge risetime  
Pulse edge falltime  
Heartbeat pulse width  
6
4
350  
ns  
ns  
µs  
Cx = 5pF  
Cx = 5pF  
THB  
300  
400  
4.4 SIGNAL PROCESSING  
Typ  
Notes  
Description  
Min  
Max  
Units  
Threshold, T1  
250  
150  
3
counts  
counts  
counts  
seconds  
counts  
Note 1  
Note 1  
Note 1  
Note 2  
Note 1  
Threshold, T2  
Hysteresis  
Slosh filter length, time  
Slosh filter length, counts  
15  
190  
Note 1: Counts of burst  
Note 2: Uninterrupted detection / non-detection: Strap option.  
- 10 -  
4.5 DC SPECIFICATIONS  
Vcc = 3.0V, Cs = 10nF, Cx = 10pF, TA = recommended range, unless otherwise noted  
Parameter  
Notes  
Description  
Min  
Typ  
Max  
Units  
VCC  
IDD  
Supply voltage  
Supply current  
2.45  
5.25  
V
µA  
20  
VDDS  
VIL  
Supply turn-on slope  
Low input logic level  
High input logic level  
Low output voltage  
High output voltage  
Input leakage current  
Load capacitance range  
Sensitivity [T1]  
100  
2.2  
V/s  
V
V
V
V
Required for proper startup  
FILT, POL  
FILT, POL  
OUT1, OUT2, 5mA sink  
OUT1, OUT2, 1mA source  
FILT, POL  
0.8  
0.6  
VHL  
VOL  
VOH  
IIL  
CX  
S[1]  
S[2]  
Vdd-0.8  
0
±1  
50  
µA  
pF  
0.125  
0.33  
pF/count  
pF/count  
Cs = 20nF, Cx = 10pF  
Cs = 20nF, Cx = 30pF  
Sensitivity [T2]  
FIGURE 4-1  
FIGURE 4-2  
Gain vs. Cx Load; Cs = 20nF; Vcc = 3.0  
Signal Level vs. Cx Load; Cs = 20nF; Vcc = 3.0  
18  
16  
14  
12  
10  
8
6
4
2
400  
350  
300  
250  
200  
150  
100  
50  
0
0.00  
0
0.00  
10.00  
20.00  
30.00  
40.00  
10.00  
20.00  
30.00  
40.00  
Cx Load, pF  
Cx Load, pF  
4.6 PACKAGING  
AVAILABLE TYPES:  
DIP-8  
0.26" / 6.5mm body, 0.100" pitch, plastic  
D suffix  
S suffix  
SO8N 0.15" / 3.9mm body, 0.050" pitch, plastic  
Refer to QT110 datasheet for complete dimensional information  
4.7 CUSTOMIZATION  
QT114 technology can be customized to suit specific requirement, often with little NRE charge or change in part cost.  
Consult your rep or the factory for further information, or email to: sales@qprox.com  
- 11 -  
Quantum Research Group Ltd  
©1999 QRG Ltd.  
QProx, QTouch, QLevel, and HeartBeat are trademarks of QRG Ltd.  
Patented and patents pending  
651 Holiday Drive Bldg. 5 / 300  
Pittsburgh, PA 15220 USA  
Tel: 412-391-7367 Fax: 412-291-1015  
admin@qprox.com  
http://www.qprox.com  
In the United Kingdom  
Enterprise House, Southampton, Hants SO14 3XB  
Tel: +44 (0)23 8045 3934 Fax: +44 (0)23 8045 3939  
Notice: This device expressly not for use in any medical or human safety related application  
without the express written consent of an officer of the company.  
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